36
Chapter
4.System Planning
4.2. Transceiver
Planning
37:R fc
PFD
s~~\
hS
— \ '
VCO
:P(+1)<-«-
< ' 11
Mod V
:NR
V
:NS
1
'r
ii An =ita
Reset
Figure
4.6: Pulseswallowing frequency synthesizer.
hasto be 50 il.
•
Any
out-of-bandspurious signal
such as harmonicsgenerated by
nonlinearities of the PA are
greatly
attenuatedby
the filter.In
addition,
since theamplifier
is drivenby
thefrequency synthesizer
which is also active
during
the receive timeslots,
the PA mustprovide
anoffstate with
high signal
attenuation.Any spurious signal
emittedby
the PAduring
the receive time slots becomes in fact a receiverblocking signal
2 MHz from the desiredsignal.
The transmitter is based on an
integer-N PLL,
the reference fre¬quency of which hastobe a
multiple
of 1 MHz. For thepresent proto¬type
implementation
we use 13 MHz as,being
the referencefrequency
used in GSM
phones, good quality,
low costcrystals
arewidely
avail¬able. The minimum
required
VCXOtuning
range toproperly
modulatethe carrier
frequency
is ±66 ppm. To allow formanufacturing
toler¬ancesandtemperature
variations,
wetargetatuning
rangeof ±90ppm.Concerning
powerconsumption,
one of the most critical compo¬nents of the transmitter is the
frequency
dividerdividing
the VCOfrequency.
Since afully programmable
counterworking
at the VCOfrequency
is notpractical,
we realize the dividerby
thecommonpulse
swallowing technique
shown inFig.
1 6[V]. By combining
a fast butsimple prescaler
P with twoprogrammable
countersNr
andNs,
any38
Chapter
4.System Planning
image-rejectmixer
Figure
4.7: Blockdiagram of
thecomplete
transceiverdivision ratio
Nr
+ PNs larger
orequal
to P(P
—1)
and withNr
>Ns
can be achieved Thesimplest
and most power efficient dual modulusprescalers
are those with Pbeing
a power of two Tocover all of the Bluetooth channels the maximal
possible
value for Pis32 The
programmable
countersR, Nr,
andNs
work atfrequencies
lower than 80 MHz
Therefore,
a standard cellimplementation
doesnotpresent any
disadvantage
Since for theimplementation
ofourpro¬totype no
library
wasavailable,
theprogrammable
counters and thephase-frequency
detector(PFD)
have not beimplemented
The block
diagram
of the wholetransceiverisdepicted
inFig
I 7 Thedashed line represent the border of the IC The gray area shows the part of the systemwhich has notbeen
implemented
on the prototype The details of theimplemented
blocks are discussed inChapters
6 andChapter 5
0.18 /im CMOS
Technology
For the present
design
a 0.18 /jmfoundry
CMOS process was used.CMOS is not the best
technology
choice from theperformance point
of view. Thegain
and noise characteristics ofanalog
circuits are infact
strongly dependent
from the transconductancegm of the active de¬vices. Even
though
the transitfrequency fp
of moderndeep-submicron
CMOS
technologies
iscomparable
to that of silicon(Si) bipolar
ones, the grm-to-current ratioof MOS transistors isalways
lower than that of BJTs.Hence,
animplementation
with a Sibipolar technology,
orwitha
technology
with ahigher
carriermobility
such as a GaAs MESFETorBJT processwould result in a lower power
solution,
orina solutionwith a better
performance
at the samepowerconsumption
level.On the other
hand,
CMOS offersverylarge
scaleintegration
capa¬bilities,
is costeffective,
and is thetechnology
with the mostextensivecatalog
of libraries and intellectual property(IP)
cores,ranging
from standard-cells tomicroprocessors.
CMOS is thus the mostappropriate technology
for theimplementation
ofasingle chip solution,
which wasthe main motivation behind the choice of a CMOS process.
39
40
Chapter
5. 0.18 /Lxm CMOSTechnology
5.1 CMOS for RF and Analog Design
From the RF
designer point
ofview,
the mainchallenges
of adeep-
submicron CMOS
technology
are:• Low
supply voltage:
one of thedisadvantages
ofdeeply
scaledCMOS
technologies
foranalog designs
is the lowsupply voltage.
The
supply voltage
isdecreasedtolimit electrical fields within the devices and thus avoid breakdown. Asscaling
ismainly
drivenby digital designs
to increasedensity
andspeed,
the thresholdvoltage Vp
of the devices is not scaledproportionally.
This isbecause the
leakage
currents ofdigital
circuitsdepend,
to firstorder, exponentially
on —Vp.
This trend limits the number of devices that can bestacked,
andfrequently precludes
the use ofcascodestructures which areoften used to reduce the Miller ca¬
pacitance,
increase thesmall-signal
drain-sourceimpedance,
andto
accurately
copybias currents of matched circuits.Moreover,
the maximal
practical
overdrivevoltage (Vos
—Vf)
whichsetsthesmall
signal linearity
ofa MOSdevice,
and the maximalswing
of internal nodesare also reduced.•
1/f
noise: Flicker noise of MOS transistorscanberepresented by
an
equivalent
gatevoltage
noise generator^7
=WLCUAF 'A/ (5-1}
where
Kp
andAF are processdependent
parameters,C'ox
is thegateoxide
capacitance
perunit area, W and Lare the width andlength
of the transistor's gate, and/
is thefrequency.
It is notuncommonfor the flicker noise tobe the dominant noise compo¬
nent well into the
megahertz
range. As anexample,
whereas the thermalvoltage
noisespectral density
referred to the gate ofa W = 100 lira, L = 0.18 /jm nMOS transistor biased in satura¬tion and with gm = 10 mS is 1.06
nV/yTIz,
the flicker noise at 2 MHz ofatransistorintegrated
with thetechnology
used for thisproject
with thesamegeometryis 6.7nV/i/Hz.
FromEq. (5.1 )
itis clear that flicker noise canbe reduced
by increasing
the activearea W L of the
transistor,
but this also results in an increase of the transistor'sparasitic capacitances
and may notalway
be5.2. The TSMC Process 41
convenient. In
spite
of the fact that the power of1/f
noise isconcentrated at "low"
frequencies
and is thereforeunimportant
inlinearhigh frequency
circuitssuchasamplifiers,
itmayplay
animportant
role inhigh frequency
nonlinear circuits suchasmixers andoscillators,
and in the IFstrip
ofa low-IFordirect conversion receiver.• Substrate
Coupling:
Therelatively highly doped
common sub¬strate not
only
influences the electrical characteristics of thetran¬sistors,
but it alsocreates unwanted feedbackpaths
between dif¬ferent nodes of the same
circuit,
and even between different cir¬cuits
[2*]. Moreover,
the substrate also limits the maximalqual¬
ity
factorQ
ofresonant structures and inparticular
ofintegrated spiral
inductors to values around 5-10.5.2 The TSMC Process
Some
important
characteristics of the TSMC 0.18 /jm CMOS process used for thisproject
aresummarized in Table 5 1. This CMOS process is basedon ap-typesubstrate,
and has 1poly
and 6 metallayers.
Theprocessoffers athicktopmetal
option
for theimplementation
of"high- Q" spiral inductors,
whichunfortunately
was not available on MPWruns. The process also offers
(optional) high-quality
metal-insulator- metal(MIM) capacitors.
To reduce noise
coupling through
the substrate the process offersa
high
energyDeep-N-Well (DNW) implant.
A DNW surroundedby
an N-Well
strip
may be usedtoisolatep-typeregions (called R-Wells)
from the substrate. This way the isolation between different parts of the IC can be
greatly improved [;" '].
This feature can beeffectively
used to isolate sensitive parts of
analog
circuits from fastswitching
digital
circuits.42
Chapter
5. 0.18 /Lxm CMOSTechnology
Process Substrate Metals
Supply Voltage
l'ox
p-type/Triple
Well6
layers
1.8 V